Research Article  Open Access
J. Mar, K. C. Tsai, Y. T. Wang, M. B. Basnet, "Intelligent Motion Compensation for Improving the Tracking Performance of Shipborne Phased Array Radar", International Journal of Antennas and Propagation, vol. 2013, Article ID 384756, 14 pages, 2013. https://doi.org/10.1155/2013/384756
Intelligent Motion Compensation for Improving the Tracking Performance of Shipborne Phased Array Radar
Abstract
The shipborne phased array radar must be able to compensate the ship’s motion and track the maneuvering targets automatically. In this paper, the realtime beam pointing error compensation mechanism of a planar array antenna for ship’s motion is designed to combine with the Kalman filtering. The effect of beam pointing error on the tracking performance of shipborne phased array radar is examined. A compensation mechanism, which can automatically correct the beam pointing error of the planar antenna array, is proposed for shipborne phased array radar in order to achieve the required tracking accuracy over the long dwell time. The automatic beam pointing error compensation mechanism employs the parallel fuzzy basis function network (FBFN) architecture to estimate the beam pointing error caused by roll and pitch of the ship. In the simulation, the models of roll and pitch are used to evaluate the performance of beam pointing error estimation mechanism based on the proposed parallel FBFN architecture. In addition, the effect of automatic beam pointing error compensation mechanism on the tracking performance of adaptive extended Kalman filter (AEKF) implemented in ship borne phased array radar is also investigated. Simulations find out that the proposed algorithms are stable and accurate.
1. Introduction
Beam pointing error caused by ship motion over the ocean affects the tracking performance of the shipborne phased array radar. The antenna stabilization to achieve the beam pointing accuracy over the long dwell time is an important issue for shipborne phased array radar [1]. There are two ship motion compensations: compensation for rotational motion (i.e., pitch, roll, and heading angle) and compensation for translational motion (i.e., radial speed relative to the earth). Figure 1 shows the shipborne phased array radar system [2, 3], which consists of the gyro sensor, beam steering controller (BSC), array antenna, radar control computer (RCC), digital signal processor (DSP), transmitter and receiver (XMTR/RCVR), and display. Gyro sensor provides pitch, roll, heading angles of the ship, speed, course, vertical velocity of antenna installed on the ship at a data rate of 100 Hz. To compensate the translational motion, the speed, course, and vertical velocity acquired from the Gyro sensor are averaged for the duration of radardwell time. Then the Doppler shift introduced by the translational motion is calculated to compensate the radial velocity estimated in the digital signal processor (DSP). The radar control computer (RCC) provides the target locations relative to earth, scheduled beam directions, and predicted beam pointing error to the beam steering controller (BSC), which compensate the beam pointing error and controls the phased array antenna to point the beam at the target direction relative to the ship coordinates.
The idea of the extended Kalman filter (EKF) was originally proposed by Stanley Schmidt so that the Kalman filter could be applied to nonlinear spacecraft navigation problems [4]. The wellknown conventional EKFs give the optimal solution but require synchronous measurements, an accurate system model, and exact stochastic noise characteristics. Thus, the performance of EKF with incomplete information and asynchronous sensors measurements may be degraded or even diverged. In order to reduce the effect of noise variance uncertainty, adaptive extended Kalman filter (AEKF) is proposed to overcome this drawback.
In this paper, we focus on the design of an automatic beam pointing error correction mechanism based on the proposed parallel fuzzy basis function network (FBFN) architecture, which predicts the beam pointing error caused by roll and pitch in real time. The AEKF algorithm is used to track the air target in threedimensional space, and the covariance matrix values of process noise and measurement noise are adaptively estimated to ensure the AEKF convergence.
The rest of this paper is organized as follows: the model of ship rotational motion, coordinates transform and planar array antenna of shipborne phased array radar are described in detail in Section 2. The architecture of parallel FBFN beam pointing error estimator is presented in Section 3. The AEKF algorithm is described in Section 4. In Section 5, the tracking performance of shipborne phased array radar using the proposed beam pointing error compensation method is simulated for six different cases. Finally, we conclude the paper in Section 6.
2. Ship Rotational Motion Compensation
The shipborne phased array radar must be able to compensate the ship’s motion and track the maneuvering targets automatically. The algorithm of realtime compensating for ship’s motion is designed to combine with the Kalman filtering. The block diagram of rotational motion compensation system for shipborne phased array radar is shown in Figure 2 [3], which consists of beam pointing error prediction, ship coordinates/earth coordinates conversion, earth coordinates/ship coordinates conversion, and adaptive extended Kalman filter (AEKF). Assume that the beam steering angle is , the antenna point angle offset caused by the ship motion (roll, pitch) is , and then the current antenna pointing angle is as
If the beam pointing error is predicted as , then the beam pointing angle is corrected as The is approximated to .
2.1. Ship Rotational Motion Model
Ship is affected by the waves in the ocean, resulting in six degrees of freedom of movement. In this paper, assuming zero yaw angle, the simplified roll and pitch model [1, 5] are adopted to describe the ship rotational motion in the earth coordinates. Ship's rotational motion is modeled with sinusoidal signal. The roll angle is The pitch angle is where and are the amplitude of ship’s roll and pitch angles, and are assumed to be zero mean Gaussian noise, and are the roll and pitch periods, and and are the roll and pitch angular frequencies. The beam pointing errors caused by other unknown factors, including ship’s traveling direction changing and whether changing, in the actual ship navigation environment will be considered in the standard deviation of the noise terms. The amplitude and period parameters of sea states 4, 5, and 6 are listed in Table 1 [1].

2.2. Coordinates Transform
Since the phased array antenna is installed on the ship, the beam steering control employs the ship body coordinates. But the target tracking of Kalman filter employs the Earth coordinates. The Euler coordinates transform formula is used to convert antenna beam pointing angle relative to the earth into antenna beam pointing angle relative to the ship body [5] as
where the coordinates transform matrices are defined as where is the ship roll angle, is the ship pitch angle, and is the ship yaw angle.
2.3. Planar Array Antenna
An element planar array, as shown in Figure 3, is designed for the shipborne phased array radar system, which includes the beamforming (BF) mode and direction of arrival (DOA) mode. The planar array can produce multibeams in the azimuth and elevation by using the beamformer network (BFN), which consists of a set of power dividers and phase shifters. The planar array using amplitude comparison method [6] generates the difference signal patterns for the DOA estimation. The difference signals obtained from two neighboring beams can measure the DOA of the subscriber signal of the shipborne phased array radar system. The beam pattern is expressed as [6, 7] where where = = Chebyshev weighting [5], = the number of array elements in the axis, = the number of array elements in the axis, = the azimuth steering angle of the main beam, = the elevation steering angle of the main beam, = the interelement spacing in the axis, and = the interelement spacing in the axis.
The phase of the RF signal at each array element is adjusted to steer the beam to the coordinates . For and , the computed antenna radiation pattern of a beam steered to is shown in Figure 4. The sidelobe suppression is −30 dB by using the Chebyshev weighting = [0.54 0.78 1 1 0.78 0.54]. The 6 × 6 planar array antenna is chosen to simulate the beam pointing error compensation and the tracking accuracy of maneuvering target position .
3. Parallel FBFN Architecture
The beam pointing error of the shipborne phased array radar over the ocean is always changing from time to time, so it is necessary to intelligently predict and compensate the beam pointing error through the collected ship’s roll and pitch angles data. For reducing the computation load and meeting the realtime requirement of the automatic beam pointing error correction system, a simplified parallel FBFN architecture, which makes use of the roll angle and pitch angle measurements mapped onto the beam pointing error model to nonlinearly estimate the angle error of the planar antenna array, is proposed. The parallel FBFN architecture is shown in Figure 5, which is implemented with fourlayer feed forward network. The input vectors including beampointing angles at the time , , , are input to membership functions to determine its membership grade.
The RLS algorithm and the FBFN algorithm with the properly normalized Gaussian membership function are employed to automatically correct the beam pointing error caused by the ship’s roll angle and pitch angle. The beam pointing error correction mechanism using the RLS algorithm is realized with a th order adaptive prediction filter. The RLS algorithm is summarized as follows [8].
Initialize ,
At each instant of time, , compute inverse correlation matrix as The gain vector is The predicted correction angle is obtained by The estimation error is where is the beam point error at time instant. The update weightings of the prediction filter are The RLS algorithm is convergent if the following condition is satisfied: where is the variance of the Gaussian distribution of beam pointing error for pitch angle. The forgetting factor is a constant in (0, 1). Here we assume that , , and .
The FBFNbased beam pointing error correction mechanism of the LMDS system is shown in Figure 7. The FBFN is a 4layer feed forward network. The input vectors include beampointing angles at . In the first layer, the rule base contains Takagi and Sugeno’s type fuzzy ifthen rules [9, 10]. The normalized Gaussianshaped membership functions are where the input vector could be pitch or roll ; “” represents Euclidean form. , are the mean vectors of the Gaussian membership functions for ship’s roll or pitch, which are generated by different sea states as where the discrete sampling time is and is the sampling frequency. Each mean vector consists of samples of the normalized Gaussian function with corresponding mean to the sampled sinusoidal signal value. The standard deviation determines the range of Gaussian membership functions for ship’s roll or pitch.
The input pitch vector is given by where “” means transpose. The ratio of the th rule’s firing strength to the sum of all rule’s firing strengths is calculated in the th node as For convenience, the outputs of this layer are called “normalized firing strength.” The output of the third layer is The consequent parameters are where is the coefficients of the consequent parameters. The consequent parameter vector is The output of the fourth layer is obtained as The matrix form of FBFN beam pointing error estimator can be expressed as whereEach input training vector correspond to one row in the matrix, which contains data elements. Therefore, must be greater than or equal to in order to solve the consequent parameters. The vector of the desired output in fuzzy inference rules is defined as
A reinforcement learning scheme termed the leastsquare estimator (LSE) is used to optimally adjust in layer three for approximating the desired output of FBFN beam pointing error estimator. The consequent parameter vector is trained as
4. Adaptive Extended Kalman Filter [4]
The AEKFbased target tracking algorithm [11, 12] is used by shipborne phased array radar to recursively update the linear and nonlinear target trajectories and it further improves its tracking accuracy. The distance between the flying target and radar at a time point is represented as where and are the coordinates of radar and air target, respectively. As shown in Figure 3, in polar coordinates, the horizontal angle is expressed as The vertical angle is expressed as The system state equation in matrix form is where is the target state vector, where , , , are the relative position of the target in the  and axes and relative velocity in the  and axes, respectively. The relative acceleration in the  and axes is defined as modeling error , which is assumed to be random with white Gaussian noise (WGN). is the detection cycle time. The transition matrix is The measurement equation in matrix form only considers the position measurements in , , and , which are not linear equation as where is assumed to be zero mean WGN. The nonlinear equation (32) is linearized by using the firstorder Taylor approximation as where the measurement matrix is
From (34), the linear measurement equation is redefined as where The covariance matrix of process noise is defined as The covariance matrix of measurement noise is defined as Due to the impact of ship movement and environmental noise, process noise and measurement noise will dynamically change, so that the covariance matrix values of process noise and measurement noise are adaptively estimated to ensure the extended Kalman filter convergence. The covariance matrix of measurement noise is obtained with where where the residual value is the difference between measurement and estimation, and is the moving window size. The covariance matrix of process noise is obtained with The flow chart of AEKF algorithm is shown in Figure 6.
5. Computer Simulations
Six scenarios are used to simulate the tracking performance of shipborne phased array radar using the proposed beam pointing error compensation mechanism.
Case 1 (beam pointing error compensation for stationary ship and target). The ship’s roll and pitch signals are simulated according to (3) and (4) with roll and pitch angle parameters of sea state 5 listed in Table 1 and standard deviation of 0.05. The beam of 6 × 6 planar array antenna is steered to . The sampling frequency is set as 100 Hz. Therefore, the ship’s roll and pitch signals are sampled 1000 points within 10 seconds, which is used as the center value of 1000 membership functions for parallel beam pointing error estimator. The simulated ship’s roll and pitch signals are applied for the FBFN architecture and the RLS adaptive prediction filter to simulate the performance of pointing error estimation. Each of the ship’s roll and pitch signals is sampled 13 points for each of simulations. The simulation replicates 1000 times. The input samples are updated by one new sample for the next iteration. Figures 7 and 8 compare the ensembleaveraged square error performance of the FBFN architecture and RLS adaptive prediction filter for roll and pitch angles, respectively, per 0.01 sec iteration time. Table 2 compares the convergent values of ensembleaveraged square beam pointing error for FBFN architecture and RLS adaptive prediction filter under different sea states and standard deviation of 0.05. The ensembleaveraged square error is defined as
where represents the th MonteCarlo simulation; represents the number of the iterations.
Based on the simulation results, we may make the following observations. The FBFN architecture converges much faster than the RLS adaptive prediction filter and it has lower ensembleaveraged square error than RLS adaptive prediction filter. The steady state values of the ensembleaveraged square error for both the FBFN architecture and RLS adaptive prediction filter approximate to the standard deviation of the Gaussian noise. In summary, the convergent time and accuracy of the automatic beam error correction system using the FBFN architecture is superior to the RLS adaptive prediction filter. The shortest convergent time is 0.1 sec when FBFN beam pointing error estimator is used (see Table 3).


Case 2 (beam pointing error estimation and compensation for linear moving ship and target). Figures 9(a) and 9(b) shows the simulation scenario of beam pointing error compensation for linear moving air target and ship with linear motion. Assuming the ship is along the axis of plane in the earth coordinates, the ship speed is 10 m/sec and the flying target speed is 300 m/sec. The flying target is parallel to the plane, 9.84 km above the ground, and the angle between the flight direction and the axis is 30°. The largest reconnaissance distance of shipborne radar is 150 km. while the air target is flying within the radar detection range, the beam pointing error estimation and compensation of shipborne phased array radar are simulated.
The linear ship path equation is
where sec, is ship velocity, and is initial ship position. The linear target trajectory equation is
where is the target velocity, and is the initial target position.
Figures 10(a) and 10(b) compare the beam pointing error compensation performance of the FBFN architecture, RLS adaptive prediction filter for roll and pitch angles, respectively, under the sea state 5 condition. The green curve represents the real beam steering angle of the shipborne phased array radar. The initial beam angle is steered to , and the following beam angles are calculated by (20) and (21). The FBFN architecture converges faster than the RLS adaptive prediction filter. The peak response of the RLS adaptive prediction filter will result in the performance degradation of the shipborne phased array radar.
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Case 3 (beam pointing error estimation and compensation for linear moving ship and circular trajectory target). Figures 11(a) and 11(b) show the simulation scenario of beam pointing error compensation for circular maneuvering air target and linear moving ship. The ship has the same linear moving speed and path equation. The flying target is parallel to the plane, 9.84 km above the ground, and the angle between the initial position and the axis is 30°. The trajectory of the equal speed flight vehicle is a circle with a radius of 10 km, and the axis is the center. The rotational cycle time of the flight target is 209 seconds.
The circular trajectory equation is
where sec, is the circular flight radius, is the initial angle between the flight vehicle and the axis, and is the angular speed of flight vehicle.
When the vehicle flies in circles with constant speed, the simulation results for roll and pitch angles are shown in Figures 12(a) and 12(b), respectively. The FBFN architecture converges faster than the RLS adaptive prediction filter and compensates the beam pointing error effectively.
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Case 4 (AEKF with no beam pointing error for linear trajectory target). Assuming the ship is not affected by the sea waves (antenna beam pointing error is zero), the tracking performance of AEKF for a straight flight target trajectory is simulated. As shown in Figure 13, the initial position of radar is . The ship moves with a speed of 10 m/sec in the axial direction. The radar position is updated every second. The initial position of flying targets is −74840, −129620, and 9100 meters, about 150 km from the radar. The flight speed of target is 300 m/sec ( axial velocity of 150 m/sec and axial velocity of 260 m/sec). The target location is updated every second. The tracking accuracy of AEKF for a straight flight target is shown in Figure 14, where the trajectory estimation error is calculated by It shows that the AEKF converges to less than about 20 m after 550 iterations.
Case 5 (AEKF with no beam pointing error for circular trajectory target). Assuming the ship is not affected by the sea waves (antenna beam pointing error is zero), the tracking performance of AEKF for a circular trajectory target is simulated. As shown in Figure 15, the initial position of radar is . The ship moves with a speed of 10 m/sec in the axial direction. The radar position is updated every second. The initial position of flying targets is −5000, −8660, and 9100 meters about 13.5 km from the radar. The flying target is parallel to the plane, 9.84 km above the ground, and the angle between the initial position and the axis is 30°. The flying object has uniform velocity and circular trajectory of radius of 10 km, and the axis is the center. The rotational cycle time of the flying target is 209 seconds. The target flies two cycles in the simulation. The tracking accuracy of AEKF for a circular trajectory flight target is shown in Figure 16. The AEKF converges to less than 1 m after 100 iterations, because the distance between radar and flight target in Case 3 is less than Case 5.
Case 6 (combining AEKF with beam pointing error compensation for linear trajectory target). Figure 17 is a simulation flow chart used to verify the effect of beam pointing error compensation on AEKF tracking accuracy. The shipbone radar and flight target have the same experimental scenario as Case 4, but beam pointing error generated by roll and pitch angle parameters of sea state 5 is considered. The linear trajectory target is shown in Figure 13.
When the beam pointing of shipborne phased array antenna is affected by the roll and pitch angles, the target tracking error of AEKF is shown in Figure 18. It shows that the AEKF converges to less than about 20 m at 550 iterations but the estimation error increases to 100 m at 1000 iterations. We conclude that the tracking accuracy is affected by the beam pointing error and the increasing distance between the radar and flight target obviously when the simulation result of Figure 18 is compared with Figure 14. When the beam pointing error of shipborne phased array antenna is compensated with FBFN controller, the target tracking error of AEKF is shown in Figure 19. It shows that the tracking error of AEKF converges to less than about 20 m at 550 iterations and the estimation error will remain within the range of about 20 m when beam pointing error is compensated by FBFN controller. The error compensation values of FBFN controller are shown in Figure 20, which is calculated by subtracting the trajectory estimation error of Figure 18 from Figure 19. The error compensation values of FBFN controller present a Vshaped curve. The tracking performance of AEKF is proportional to the distance between moving target and the ship. In the simulation of the starting point and end point, moving targets far from the shipborne radar, the FBFN controller generates the largest estimation error. When the moving target closes the radar just above the ship, the FBFN controller generates the smallest estimation error.
6. Conclusions
This paper proposed an intelligent beam pointing error compensation mechanism for shipborne twodimensional phase array antenna radar. The FBFN controller estimates the roll and pitch angle of the ship driving in the sea and thus compensates for the antenna beam pointing error in order to enhance the accuracy of phased array radar system tracking a moving target. Six cases of simulations are used to verify the performance of shipborne phased array radar using the proposed beam pointing error compensation mechanism for six different scenarios. Cases 1, 2, and 3 simulate the accuracy of beam pointing error compensation mechanism and Cases 4, 5, and 6 simulate the effect of beam pointing error compensation mechanism on the tracking accuracy of AEKF.
The simulation results show that the convergent time and accuracy of the automatic beam pointing error compensation mechanism using the FBFN architecture are superior to the RLS adaptive prediction filter. The tracking accuracy is affected by the beam pointing error and the distance between the radar and moving target. In summary, the use of the proposed FBFN beam pointing error compensation mechanism with the AEKF can reduce the amount of estimation error significantly.
Acknowledgment
This work is supported in part by research grants from the National Science Council, Taiwan (NSC 1022218E155001).
References
 Z. Fang and Q. Rundong, “Shipborne phased array radar motion compensation,” in System Engineering and Electronic Technologies, pp. 4–8, 1998. View at: Google Scholar
 S. L. Chen, Modeling, dynamics and control of large amplitude motion of vessel in beam seas [Ph.D. thesis], Department of Mechanical Engineering, Michigan State University, 1996.
 L.X. Wang, “Stable adaptive fuzzy control of nonlinear systems,” IEEE Transactions on Fuzzy Systems, vol. 1, no. 2, pp. 146–155, 1993. View at: Publisher Site  Google Scholar
 V. Fathabadi, M. Shahbazian, K. Salahshour, and L. Jargani, “Comparison of adaptive Kalman filter methods in state estimation of a nonlinear system using asynchronous measurements,” in Proceedings of the World Congress on Engineering and Computer Science (WCECS '09), vol. 2, pp. 20–22, San Francisco, Calif, USA, October 2009. View at: Google Scholar
 D. C. Law, S. A. McLaughlin, M. J. Post et al., “An electronically stabilized phased array system for shipborne atmospheric wind profiling,” Journal of Atmospheric and Oceanic Technology, vol. 19, no. 6, pp. 924–933, 2002. View at: Google Scholar
 C. A. Balanis, Antenna Theory: Analysis and Design, John Wiley & Sons, 3rd edition, 2005.
 J. Mar and Y.R. Lin, “Implementation of SDR digital beamformer for microsatellite SAR,” IEEE Geoscience and Remote Sensing Letters, vol. 6, no. 1, pp. 92–96, 2009. View at: Publisher Site  Google Scholar
 S. Haykin, Adaptive Filter Theory, Prentice Hall, 3rd edition, 1996.
 E. Mosca, Optimal, Predictive, and Adaptive Control, Prentice Hall, 1995.
 Y. Li and Y.T. Jang, “Complex adaptive fuzzy inference systems,” in Proceedings of the Asian Fuzzy Systems Symposium, pp. 551–556, December 1996. View at: Google Scholar
 A. Almagbile, J. L. Wang, and W. Ding, “Evaluating the performance of adaptive Kalman filter methods in GPS/INS integration,” Journal of Global Positioning System, vol. 9, no. 1, pp. 33–40, 2010. View at: Google Scholar
 K. H. Kim, J. G. Lee, and C. G. Park, “Adaptive twostage extended kalman filter for a faulttolerant INSGPS loosely coupled system,” IEEE Transactions on Aerospace and Electronic Systems, vol. 45, no. 1, pp. 125–137, 2009. View at: Publisher Site  Google Scholar
Copyright
Copyright © 2013 J. Mar et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.